**Parameters Estimation of Time-Varying Harmonics**

Cristiano A. G. Marques, Moisés V. Ribeiro, Carlos A. Duque and Eduardo A. B. da Silva

Additional information is available at the end of the chapter

http://dx.doi.org/10.5772/53816

### **1. Introduction**

[13] Eslami M., Shareef H., Mohamed A., Khajehzadeh M., Particle swarm optimization for simultaneous tuning of static var compensator and power system stabilizer, Elec‐

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[16] Piasecki Sz., Jasiński M., Rafał K., Korzeniewski M., Milicua A., Higher harmonics compensation in grid-connected PWM converters for renewable energy interface and

[17] Pasko M., Lange A., Compensation of the reactive power and filtration of high har‐ monics by means of passive LC filters, Electrical Review 04/2010, 126-129

[18] Rivas D., Morán L., Dixon J. W., Spinoza J. R., Improving passive filter compensation performance with active techniques, IEEE Transactions on Industrial Electronics, vol.

[19] Świątek B. Hanzelka Z., Neural network-based controller for an active power filter. 10th International Power Electronics & Motion Control Conference, September 9-11,

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[21] Świątek B., Hanzelka Z., A single-phase active power filter with neural networkbased controller, IASTED International Conf. Power and Energy Systems, July 3-6,

[22] Świątek B., Klempka R., Kosiorowski S., Minimization of the source current distor‐ tion in systems with single-phase active power filters and additional passive filter designed by genetic algorithms, 11th European Conference on Power Electronics and

[23] Varetsky Y., Hanzelka Z., Klempka R., Transformer energization impact on the filter performance, 8th International Conference on Electrical Power Quality and Utilisa‐

[24] Varetsky Y., Hanzelka Z., Filter characteristics in a DC drive power supply system, 13th International Conference on Harmonics & Quality of Power, Australia, 28th

[25] Vishal V., Bhim S., Genetic-algorithm-based design of passive filters for offshore ap‐ plications, IEEE Transactions on Industry Applications, vol. 46, no. 4. July/August

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September–1st October 2008

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230 Power Quality Issues

50, no. 1, February 2003

2001, Rhodes, Greece

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active filtering, Electrical Review 06/2011, 85-90

The increasing use of power electronic devices in power systems has been producing significant harmonic distortions, what can cause problems to computers and microproces‐ sor based devices, thermal stresses to electric equipments, harmonic resonances, as well as aging and derating to electrical machines and power transformers [1–3]. The most impor‐ tant problems that have been reported in the literature concerns to the difficulty of the frequency control within the micro-grids and the increase of the total harmonic distortion. These two factors may negatively impact on the protection system, power quality analysis and intelligent electronic devices (IEDs), in which digital algorithms assume that the fundamental frequency is constant. Based on this fact, there has been an increasing interest in signal processing techniques for detecting and estimating harmonic components of timevarying frequencies. Their correct estimation has become an important issue in measure‐ ment equipment and compensating devices. Although many methods have been proposed in the literature, it still remains difficult to detect and estimate harmonics of time-varying frequencies [4, 5]. The harmonic components (voltage or current) can change its frequen‐ cies due to continuous changes in the system configuration and load conditions, to the rapid proliferation of distributed resources, and to possibilities of new operational scenarios (e.g., islanded microgrids). Also the need for massive monitoring of networks is unquestionable within the concept of *smart grids*. An important line of research in the *smart grids* context is to identify and estimate time-varying harmonics that may appear in the current and voltage signals, and from this information, correct and adjust the digital algorithms that are part of protection equipments, power quality monitors and IEDs.

The concept of time-varying harmonics came recently to the vocabulary of power systems engineers, because more and more nonlinear loads, with dynamic behavior, are being

connected to power systems and the fundamental frequency is experiencing a large range of variation. These factors have putting in check the traditional stationary spectral analysis methods, and many techniques for improving harmonics measurement have been proposed in recent years. Parametric and nonparametric methods that commonly have been used by the community of signal processing have been applied to power system harmonic estimation. These methods have in common that they need to estimate the fundamental frequency to adjust some internal parameters, like filter coefficients. The challenge is producing a harmonic estimator with high convergence ratio, high accuracy, low computational burden and im‐ munity to the presence of interharmonic: conditions that are not ease to simultaneously deal with. The most used technique for harmonics estimation is based on the discrete Fourier transform (DFT) [8, 10]. The DFT algorithm is attractive because of its low computational complexity and its simple structure. However, DFT does not perform well if power system frequency varies around the nominal value. Several other techniques have been proposed in the literature for harmonic estimation. However, the DFT still appear to be the preferred algorithm mainly due to its simplicity.

**3. Harmonic estimation techniques: Before and after smart grid**

1

=

*Nh*

*m*

[6, 7], the frequency of the *m*-th harmonic can be defined as

*m*

*dϕ*1(*t*) *dt*

y

frequency), from (2) we have

*dt* <sup>=</sup>*<sup>m</sup> <sup>Ω</sup>*<sup>0</sup> <sup>+</sup>

*dϕm*(*t*)

*mΩ*<sup>0</sup> +

varying.

0

*t m*

f

Assuming *Ω*<sup>0</sup> constant, note that any variation in *ψm*(*t*) can be expressed by the term

<sup>1</sup> ( ) ( ). *<sup>m</sup> d t d t m dt dt*

f

The goal of harmonic estimation techniques is to provide estimates of the parameters *Am*(*t*) and *ϕm*(*t*) using the discrete version *x n* of the signal *x*(*t*). Some of the existing techniques estimate these parameters considering that the fundamental angular frequency *ψ*1(*t*) is constant and nominal (steady) and some estimate the same parameters considering *ψm*(*t*) time-

Basically, we can say that before *smart grid*s, the most used techniques for harmonic estimation assumed that *ψ*1(*t*) was constant and nominal. This is the reason that DFT is the standard algorithm adopted in international standards and implemented in the majority of equipments. It can be explained because, generally, in interconnected power systems the power frequency is high controlled and very near the nominal value. Thus, powerful harmonic estimation methods are not needed, except in especial applications. However, with the inclusion of new power generation technologies such as renewable energy source generation and distributed

f

expressed by

Consider the monitored power line signal, after processed by the analog anti-aliasing filter, be

0

where *Am*(*t*) and *ϕm*(*t*) are, respectively, the amplitude and phase of the *m*-th harmonic, *Nh* is the maximum harmonic order, *η*(*t*) is the additive noise and *Ω*<sup>0</sup> denotes the angular funda‐ mental synchronous frequency. Based on the definition of instantaneous frequency deviation

[ ( )] ( ) ( ) . *m m*

*dm t t d t*

As *ψm*(*t*)=*mψ*1(*t*) (the frequency of the *m*-th harmonic is equal to *m* times the fundamental

*dt dt*

f

0

 f

+ <sup>=</sup> = + (2)

\ = (3)

*dϕm*(*t*) *dt* .

 h

<sup>=</sup> å + + (1)

Parameters Estimation of Time-Varying Harmonics

http://dx.doi.org/10.5772/53816

233

( ) ( )cos[ ( )] ( ),

*xt A t m t t t*

*m m*

### **2. Power quality and smart grid**

The term "*smart grid*" has different definitions in the literature. Regardless of the precise definition, the term smart grid can be seen as a new paradigm, covering from conception to operation of the power systems, that makes intensive use of information and communication technologies, decentralized control approaches, powerful signal processing and computation‐ al intelligence techniques, renewable and distributed generation and storage energy facilities, self-generation, etc [11] to offer flexibility, robustness, and efficiency regarding generation, transmission, distribution, and consumption of electrical energy.

One of the promises of the *smart grid* is to improve the power quality. Therefore, the reliability or continuity of service is one of the consequences that will result from the implementation of the self-healing aspects of the Smart Grid. However power quality issues should not form an unnecessary barrier against the development of *smart grids* or the introduction of renewable sources of energy. The smart properties of future grids should rather be a challenge for new approaches in an efficient management of power quality [11].

An adequate power quality should guarantees electromagnetic compatibility between all equipment connected to the grid. Then, an important issue for the successful and efficient operation of smart grids is the introduction of advanced, flexible, robust, and cooperative set of signal processing and computational intelligent techniques for power quality analysis. With this set of techniques, an effective and extensive smart monitoring system can be devised and deployed. Such a monitoring system have to allow for the monitoring of such as voltage, current, bidirectional energy consumption at distribution transformers, substations trans‐ formers, smart meters, distribution feeders, distribution switching devices, and strategically installed power quality monitors in the power systems.

### **3. Harmonic estimation techniques: Before and after smart grid**

connected to power systems and the fundamental frequency is experiencing a large range of variation. These factors have putting in check the traditional stationary spectral analysis methods, and many techniques for improving harmonics measurement have been proposed in recent years. Parametric and nonparametric methods that commonly have been used by the community of signal processing have been applied to power system harmonic estimation. These methods have in common that they need to estimate the fundamental frequency to adjust some internal parameters, like filter coefficients. The challenge is producing a harmonic estimator with high convergence ratio, high accuracy, low computational burden and im‐ munity to the presence of interharmonic: conditions that are not ease to simultaneously deal with. The most used technique for harmonics estimation is based on the discrete Fourier transform (DFT) [8, 10]. The DFT algorithm is attractive because of its low computational complexity and its simple structure. However, DFT does not perform well if power system frequency varies around the nominal value. Several other techniques have been proposed in the literature for harmonic estimation. However, the DFT still appear to be the preferred

The term "*smart grid*" has different definitions in the literature. Regardless of the precise definition, the term smart grid can be seen as a new paradigm, covering from conception to operation of the power systems, that makes intensive use of information and communication technologies, decentralized control approaches, powerful signal processing and computation‐ al intelligence techniques, renewable and distributed generation and storage energy facilities, self-generation, etc [11] to offer flexibility, robustness, and efficiency regarding generation,

One of the promises of the *smart grid* is to improve the power quality. Therefore, the reliability or continuity of service is one of the consequences that will result from the implementation of the self-healing aspects of the Smart Grid. However power quality issues should not form an unnecessary barrier against the development of *smart grids* or the introduction of renewable sources of energy. The smart properties of future grids should rather be a challenge for new

An adequate power quality should guarantees electromagnetic compatibility between all equipment connected to the grid. Then, an important issue for the successful and efficient operation of smart grids is the introduction of advanced, flexible, robust, and cooperative set of signal processing and computational intelligent techniques for power quality analysis. With this set of techniques, an effective and extensive smart monitoring system can be devised and deployed. Such a monitoring system have to allow for the monitoring of such as voltage, current, bidirectional energy consumption at distribution transformers, substations trans‐ formers, smart meters, distribution feeders, distribution switching devices, and strategically

algorithm mainly due to its simplicity.

232 Power Quality Issues

**2. Power quality and smart grid**

transmission, distribution, and consumption of electrical energy.

approaches in an efficient management of power quality [11].

installed power quality monitors in the power systems.

Consider the monitored power line signal, after processed by the analog anti-aliasing filter, be expressed by

$$\mathbf{x}(t) = \sum\_{m=1}^{N\_k} A\_m(t) \cos[m\Omega\_0 t + \phi\_m(t)] + \eta(t),\tag{1}$$

where *Am*(*t*) and *ϕm*(*t*) are, respectively, the amplitude and phase of the *m*-th harmonic, *Nh* is the maximum harmonic order, *η*(*t*) is the additive noise and *Ω*<sup>0</sup> denotes the angular funda‐ mental synchronous frequency. Based on the definition of instantaneous frequency deviation [6, 7], the frequency of the *m*-th harmonic can be defined as

$$d\left(\boldsymbol{\nu}\_{m}(t)\right) = \frac{d[m\Omega\_{0}t + \phi\_{m}(t)]}{dt} = m\Omega\_{0} + \frac{d\phi\_{m}(t)}{dt}.\tag{2}$$

Assuming *Ω*<sup>0</sup> constant, note that any variation in *ψm*(*t*) can be expressed by the term *dϕm*(*t*) *dt* . As *ψm*(*t*)=*mψ*1(*t*) (the frequency of the *m*-th harmonic is equal to *m* times the fundamental frequency), from (2) we have

$$
\hbar m \Omega\_0 + \frac{d\phi\_m(t)}{dt} = m \left[ \Omega\_0 + \frac{d\phi\_1(t)}{dt} \right]
$$

$$
\therefore \frac{d\phi\_m(t)}{dt} = m \frac{d\phi\_1(t)}{dt}.\tag{3}
$$

The goal of harmonic estimation techniques is to provide estimates of the parameters *Am*(*t*) and *ϕm*(*t*) using the discrete version *x n* of the signal *x*(*t*). Some of the existing techniques estimate these parameters considering that the fundamental angular frequency *ψ*1(*t*) is constant and nominal (steady) and some estimate the same parameters considering *ψm*(*t*) timevarying.

Basically, we can say that before *smart grid*s, the most used techniques for harmonic estimation assumed that *ψ*1(*t*) was constant and nominal. This is the reason that DFT is the standard algorithm adopted in international standards and implemented in the majority of equipments. It can be explained because, generally, in interconnected power systems the power frequency is high controlled and very near the nominal value. Thus, powerful harmonic estimation methods are not needed, except in especial applications. However, with the inclusion of new power generation technologies such as renewable energy source generation and distributed generation energy, the fundamental frequency of micro grids and isolated systems will suffer significant variations (this fact is already noted in actual power systems). In this new scenarios, very common in *smart grid*s, new harmonic estimation techniques will be very needed and essential.

### **4. Methods for estimating steady-state harmonics**

Methods for estimating steady-state harmonics are more simple than time-varying ones, and its algorithms do not use information of the fundamental frequency of the signal under estimation. In what follows, we describe four algorithms.

### **4.1. Discrete fourier transform**

The most common and the most used technique for steady-state harmonic estimation is the discrete Fourier transform (DFT) [8-10]. The DFT method is simple and easy to be implemented in monitoring systems, but its application for time-varying harmonics is not recommended.

Given the discrete signal *x n* , the amplitude and phase of the *k*-th harmonic component can be straightforwardly estimated by the recursive equations:

$$\hat{A}\_{k}[n] = 2\sqrt{Y\_{c\_{k}}{}^{2}[n](t) + {Y\_{s\_{k}}}^{2}[n]} \tag{4}$$

The DFT algorithm is very simple and its implementation is easy for real-time application. However, if the fundamental frequency is not nominal and constant, then the estimates can

The demodulation technique presented in [15] can be used to estimate the parameters of harmonics as point out in [16]. In similar way to the DFT technique the demodulation technique

<sup>ˆ</sup> 2 2 [ ] 2 [ ]( ) [ ] *k k*

[ ] <sup>ˆ</sup> [ ] arctan , [ ]

= - ç ÷ ç ÷ è ø

<sup>0</sup> [ ] ( [ ]cos( )) \* [ ]

<sup>0</sup> [ ] ( [ ]sin( )) \* [ ],

respectively, where *h n* is the impulse response of a low-pass filter and ∗ denotes the linear

The Goertzel technique uses a second-order infinite impulse response filter to estimate the parameters of the *k*-th harmonic [17]. The Goertzel algorithm is more efficient than the Fast

Fourier Transform (FFT) when the number of harmonics to be calculated is low.

<sup>ˆ</sup> 2 2 [ ] 2 [ ]( ) [ ] *k k*

The amplitude and phase of the k-th harmonic is estimated, respectively, by

*k*

f

*k*

*k*

*n*

*k k s*

*Y n*

*Y n*

æ ö

*c*

*An Y nt Y n kc s* = + (8)

Parameters Estimation of Time-Varying Harmonics

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235

*Y n x n kw h n <sup>c</sup>* = (10)

*Y n x n kw h n <sup>s</sup>* = (11)

*An Y nt Y n kc s* = + (12)

(9)

carry significant errors.

can give erroneous results if its filter is fixed.

in which *Yck n* and *Ysk n* are evaluated by

The k-th harmonic parameters can be estimated by

**4.2. Demodulation**

and

and

convolution operator.

**4.3. Goertzel**

and

$$\hat{\phi}\_k[n] = -\arctan\left(\frac{Y\_{s\_k}[n]}{Y\_{c\_k}[n]}\right) \tag{5}$$

respectively, where,

$$Y\_{c\_k}[n] = Y\_{c\_k}[n-1] + (\mathbf{x}[n] - \mathbf{x}[n-N])\cos(k\pi c\_0) \tag{6}$$

and

$$Y\_{s\_k}[n] = Y\_{s\_k}[n-1] + (x[n] - x[n-N])\sin(k\pi v\_0),\tag{7}$$

in which *w*<sup>0</sup> =*Ω*<sup>0</sup> / *f <sup>s</sup>* is the discrete synchronous angular frequency, *f <sup>s</sup>* is the sampling rate and *N* is the number of samples within a integer number of cycles of the fundamental power signal. The DFT algorithm is very simple and its implementation is easy for real-time application. However, if the fundamental frequency is not nominal and constant, then the estimates can carry significant errors.

### **4.2. Demodulation**

The demodulation technique presented in [15] can be used to estimate the parameters of harmonics as point out in [16]. In similar way to the DFT technique the demodulation technique can give erroneous results if its filter is fixed.

The k-th harmonic parameters can be estimated by

$$\hat{A}\_k[n] = 2\sqrt{Y\_{c\_k}^{\ \ 2}[n](t) + Y\_{s\_k}^{\ \ 2}[n]} \tag{8}$$

and

generation energy, the fundamental frequency of micro grids and isolated systems will suffer significant variations (this fact is already noted in actual power systems). In this new scenarios, very common in *smart grid*s, new harmonic estimation techniques will be very needed and

Methods for estimating steady-state harmonics are more simple than time-varying ones, and its algorithms do not use information of the fundamental frequency of the signal under

The most common and the most used technique for steady-state harmonic estimation is the discrete Fourier transform (DFT) [8-10]. The DFT method is simple and easy to be implemented in monitoring systems, but its application for time-varying harmonics is not recommended.

Given the discrete signal *x n* , the amplitude and phase of the *k*-th harmonic component can

*An Y nt Y n kc s* = + (4)

<sup>ˆ</sup> 2 2 [ ] 2 [ ]( ) [ ] *k k*

[ ] <sup>ˆ</sup> [ ] arctan , [ ]

= - ç ÷

<sup>0</sup> [ ] [ 1] ( [ ] [ ])cos( )

<sup>0</sup> [ ] [ 1] ( [ ] [ ])sin( ),

in which *w*<sup>0</sup> =*Ω*<sup>0</sup> / *f <sup>s</sup>* is the discrete synchronous angular frequency, *f <sup>s</sup>* is the sampling rate and *N* is the number of samples within a integer number of cycles of the fundamental power signal.

*k k s*

*Y n*

ç ÷ è ø

*Y n Y n x n x n N kw c c* = -+ - - (6)

*Y n Y n x n x n N kw s s* = -+ - - (7)

*Y n*

æ ö

*c*

**4. Methods for estimating steady-state harmonics**

estimation. In what follows, we describe four algorithms.

be straightforwardly estimated by the recursive equations:

*k*

f

*k k*

*k k*

*n*

**4.1. Discrete fourier transform**

essential.

234 Power Quality Issues

and

and

respectively, where,

$$\hat{\phi}\_k[n] = -\arctan\left(\frac{Y\_{s\_k}[n]}{Y\_{c\_k}[n]}\right) \tag{9}$$

in which *Yck n* and *Ysk n* are evaluated by

$$Y\_{c\_k}[n] = (\mathbf{x}[n] \cos(k w\_0))^\* \, h[n] \tag{10}$$

and

(5)

$$Y\_{s\_k}[n] = (\ge[n]\sin(k\pi\_0))^\* \, h[n] \, \tag{11}$$

respectively, where *h n* is the impulse response of a low-pass filter and ∗ denotes the linear convolution operator.

### **4.3. Goertzel**

The Goertzel technique uses a second-order infinite impulse response filter to estimate the parameters of the *k*-th harmonic [17]. The Goertzel algorithm is more efficient than the Fast Fourier Transform (FFT) when the number of harmonics to be calculated is low.

The amplitude and phase of the k-th harmonic is estimated, respectively, by

$$\hat{A}\_k[n] = 2\sqrt{\hat{Y\_{c\_k}}^2[n](t) + \hat{Y\_{s\_k}}^2[n]}\tag{12}$$

and

$$\hat{\phi}\_{k}[n] = -\arctan\left(\frac{Y\_{s\_{k}}[n]}{Y\_{c\_{k}}[n]}\right) \tag{13}$$

The vector *v m* is evaluated as following

where

and

*a*

*b*

**H**

the matrix operations.

algorithms.

*m*

**H**

*m*

<sup>1</sup> [ ] ( [ ] [ ]) [ ] [ ], *T T m mm m m* - **v HH Hy** = (21)

Parameters Estimation of Time-Varying Harmonics

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237

[ ] [ [ ] [ 1] ... [ ]]*<sup>T</sup>* **y** *m xnxn xn N* = -- (22)

[ ] [ [ ] [ ]] *m mm a b* **H HH** = (23)

*h h*

(24)

(25)

*h*

*h*

*h h*

00 0 00 0

L L

L

L L

L

*w n w n Nwn wn wn Nw n*

cos( ) cos(2 ) cos( )

æ ö ç ÷ -- - <sup>=</sup>

L LL L

00 0

00 0

sin( ( )) sin(2 ( )) sin( ( ))


In this kind of technique, the number of harmonic has to be known a priori. Otherwise, the performance can be considered reduced, also, the computational complexity is higher due to

Methods for estimating time-varying harmonics consider that not only the amplitudes and phases of harmonics change, but also the fundamental frequency, and consequently, the harmonics frequencies. Thus, the frequency estimation is generally required to improve the

The main weakness of the DFT is to estimate the harmonics when the sampling frequency is not synchronous with the fundamental frequency. In order to guarantee this synchronism we

*w n N w n N Nw n N*

sin( ( 1)) sin(2 ( 1)) sin( ( 1)) [ ]

**5. Methods for estimating time-varying harmonics**

**5.1. Discrete fourier transform with sampling frequency control**

cos( ( )) cos(2 ( )) cos( ( ))


sin( ) sin(2 ) sin( )

æ ö ç ÷ -- - <sup>=</sup>

L LL L

*w n N w n N Nw n N*

00 0 00 0

*w n w n Nwn wn wn Nw n*

cos( ( 1)) cos(2 ( 1)) cos( ( 1)) [ ]

in which *Yck n* and *Ysk n* are evaluated by

$$Y\_{c\_k}[n] = \Re(X[k])\tag{14}$$

and

$$Y\_{s\_k}[n] = \mathfrak{Z}(X[k]),\tag{15}$$

where

$$\text{sIN}[k] = \exp(2\pi k)\text{s[N-1]} - \text{s[N-2]}\tag{16}$$

$$\mathbf{s}[n] = \mathbf{x}[n] + 2\cos(2\pi k / N)\mathbf{s}[n-1] - \mathbf{s}[n-2].\tag{17}$$

### **4.4. Linear least squares**

The linear least squares (LS) algorithm estimates several harmonics in one evaluation instead of a unique estimate [18]. Its advantage is the acquisition of several harmonics in only one evaluation. However the computational burden is high.

Basically, the LS algorithm has as a result the vector given by

$$\mathbf{v}[m] = \left[ a\_1[m] a\_2[m] \dots a\_{N\_h}[m] b\_1[m] b\_2[m] \dots b\_{N\_h}[m] \right]^T \tag{18}$$

Thus, the amplitude and phase of the k-th harmonic (k ∈ [1, 2,...,*Nh* ]) are given by

$$\hat{A}\_k[m] = 2\sqrt{b\_k[m]^2 + a\_k[m]^2} \tag{19}$$

and

$$
\hat{\phi}\_k[m] = -\arctan\left(\frac{b\_k[m]}{a\_k[m]}\right).
\tag{20}
$$

The vector *v m* is evaluated as following

$$\mathbf{v}[m] = (\mathbf{H}^T [m] \mathbf{H}[m])^{-1} \mathbf{H}[m]^T \mathbf{y}[m],\tag{21}$$

where

(13)

(20)

and

236 Power Quality Issues

and

where

and

**4.4. Linear least squares**

[ ] <sup>ˆ</sup> [ ] arctan , [ ]

= - ç ÷

[ ] ( [ ])

[ ] ( [ ]),

*Xk ksN sN* [ ] exp(2 ) [ 1] [ 2], = -- p

*sn xn k N sn sn* [ ] [ ] 2cos(2 / ) [ 1] [ 2]. = + p

1 2 1 2 [ ] [ [ ] [ ] ... [ ] [ ] [ ] ... [ ] ] *h h*

[ ] <sup>ˆ</sup> [ ] arctan . [ ]

æ ö = - ç ÷

*k*

*k b m*

*a m*

è ø

Thus, the amplitude and phase of the k-th harmonic (k ∈ [1, 2,...,*Nh* ]) are given by

*<sup>T</sup> m a ma m a mb mb m b m N N* **<sup>v</sup>** <sup>=</sup> (18)

<sup>ˆ</sup> 2 2 [] 2 [] [] *Am bm am k kk* = + (19)

The linear least squares (LS) algorithm estimates several harmonics in one evaluation instead of a unique estimate [18]. Its advantage is the acquisition of several harmonics in only one

*k*

f

in which *Yck n* and *Ysk n* are evaluated by

*n*

*k*

*k*

evaluation. However the computational burden is high.

Basically, the LS algorithm has as a result the vector given by

*k*

f

*m*

*k k s*

*Y n*

ç ÷ è ø

*Y n Xk <sup>c</sup>* = Â (14)

*Y n Xk <sup>s</sup>* = Á (15)

(16)


*Y n*

æ ö

*c*

$$\mathbf{y}[m] = \begin{bmatrix} \mathbf{x}[n] \mathbf{x}[n-1] \dots \mathbf{x}[n-N] \end{bmatrix}^T \tag{22}$$

and

$$\mathbf{H}[m] = [\mathbf{H}\_a[m]\mathbf{H}\_b[m]]\tag{23}$$

$$\mathbf{H}\_d[m] = \begin{pmatrix} \cos(w\_0 n) & \cos(2w\_0 n) & \cdots & \cos(N\_h w\_0 n) \\ \cos(w\_0 (n-1)) & \cos(2w\_0 (n-1)) & \cdots & \cos(N\_h w\_0 (n-1)) \\ \cdots & \cdots & \cdots & \cdots \\ \cos(w\_0 (n-N)) & \cos(2w\_0 (n-N)) & \cdots & \cos(N\_h w\_0 (n-N)) \end{pmatrix} \tag{24}$$

$$\mathbf{H}\_b[\boldsymbol{m}] = \begin{pmatrix} \sin(\boldsymbol{w}\_0 \boldsymbol{n}) & \sin(2\boldsymbol{w}\_0 \boldsymbol{n}) & \cdots & \sin(N\_h \boldsymbol{w}\_0 \boldsymbol{n}) \\ \sin(\boldsymbol{w}\_0(\boldsymbol{n} - 1)) & \sin(2\boldsymbol{w}\_0(\boldsymbol{n} - 1)) & \cdots & \sin(N\_h \boldsymbol{w}\_0(\boldsymbol{n} - 1)) \\ \cdots & \cdots & \cdots & \cdots \\ \sin(\boldsymbol{w}\_0(\boldsymbol{n} - \boldsymbol{N})) & \sin(2\boldsymbol{w}\_0(\boldsymbol{n} - \boldsymbol{N})) & \cdots & \sin(N\_h \boldsymbol{w}\_0(\boldsymbol{n} - \boldsymbol{N})) \end{pmatrix} \tag{25}$$

In this kind of technique, the number of harmonic has to be known a priori. Otherwise, the performance can be considered reduced, also, the computational complexity is higher due to the matrix operations.

### **5. Methods for estimating time-varying harmonics**

Methods for estimating time-varying harmonics consider that not only the amplitudes and phases of harmonics change, but also the fundamental frequency, and consequently, the harmonics frequencies. Thus, the frequency estimation is generally required to improve the algorithms.

### **5.1. Discrete fourier transform with sampling frequency control**

The main weakness of the DFT is to estimate the harmonics when the sampling frequency is not synchronous with the fundamental frequency. In order to guarantee this synchronism we can control the sampling frequency as shown in Fig. 1. This method reduces and can also eliminate the errors caused by the mismatch between the fundamental frequency and the sampling frequency, however, it requires a robust and controllable ADC converter and a frequency estimation algorithm. As a result, its use is not recommended.

[ ] 0.5cos 1 cos 2 . <sup>1</sup>

<sup>2</sup> , if 1 ; <sup>2</sup> [ ] 2( ) , if 1; <sup>2</sup>

<sup>ì</sup> £ £ ïï <sup>=</sup> <sup>í</sup> - <sup>ï</sup> ££ - ïî

*n N*

*Nn N n N*

<sup>2</sup> , if 1 ;

*Nn N n N*

An interesting method based on demodulation technique for estimating time-varying har‐ monics is presented in [16]. This technique can provide very accurate estimates with a

The block diagram of the demodulation technique is depicted in Fig. 3. The LP blocks imple‐ ment identical low-pass filters and the blocks COS and SIN implement the demodulation

> <sup>0</sup> [ ] cos( [ ]) *<sup>k</sup> c k d n kw n n* = +

> <sup>0</sup> [ ] sin( [ ]), *ks k d n kw n n* = +

1 0 [ ] [ 1] ( [ ] ), *k k s k nn n f*

jj

respectively. The term *φ<sup>k</sup> n* control the instantaneous frequency of the demodulation signals

 y j

j

(29)

(30)

= - + - (31)


*n N*

1 2 [ ] 2( ) 1 , if 1; 1 2

<sup>ì</sup> £ £ ïï - <sup>=</sup> <sup>í</sup>

*w n*

*<sup>N</sup> w n*

*<sup>N</sup> w n*

*N*

*N*

The triangular window has its coefficient given by

for *N* even, and

for *N* odd.

**5.4. Demodulation**

signals expressed by

(29)-(30). It is evaluated by

and

reasonable computational complexity.

*n*

æ ö æ ö = - ç ÷ ç ÷ è ø <sup>+</sup> è ø (26)

Parameters Estimation of Time-Varying Harmonics

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(27)

239

(28)

*N* p

*n*

*n*

**Figure 1.** DFT with control of the ADC sampling frequency

### **5.2. Discrete fourier transform with signal resample**

An alternative to the problem of synchronization of the sampling frequency when the sampling frequency is constant and not controllable is resampling the original signal before the harmonic estimation with the DFT. The drawback of this approach is the high computation complexity required by the resample process. Also, a frequency estimation technique is required to control the resampling process. Fig. 2 shows the block diagram of this strategy.

**Figure 2.** DFT with signal resample

### **5.3. Discrete fourier with window**

An interesting way of improving the DFT algorithm is using a window in each block of data before the evaluation of the DFT. The windowing of the data can deal with the spectral leakage of the DFT caused by the frequency deviation by adding some computational burden to the algorithm. Some windows generally used are the triangular and Hanning. The coefficients of a Hanning window are computed from the following equation:

Parameters Estimation of Time-Varying Harmonics http://dx.doi.org/10.5772/53816 239

$$w[n] = 0.5 \cos \left( 1 - \cos \left( 2\pi \frac{n}{N+1} \right) \right). \tag{26}$$

The triangular window has its coefficient given by

$$w[n] = \begin{cases} \frac{2n}{N}, & \text{if } 1 \le n \le \frac{N}{2};\\ \frac{2\{N-n\}}{N}, & \text{if } \frac{N}{2} \le n \le N-1; \end{cases} \tag{27}$$

for *N* even, and

can control the sampling frequency as shown in Fig. 1. This method reduces and can also eliminate the errors caused by the mismatch between the fundamental frequency and the sampling frequency, however, it requires a robust and controllable ADC converter and a

ADC

An alternative to the problem of synchronization of the sampling frequency when the sampling frequency is constant and not controllable is resampling the original signal before the harmonic estimation with the DFT. The drawback of this approach is the high computation complexity required by the resample process. Also, a frequency estimation technique is required to control

An interesting way of improving the DFT algorithm is using a window in each block of data before the evaluation of the DFT. The windowing of the data can deal with the spectral leakage of the DFT caused by the frequency deviation by adding some computational burden to the algorithm. Some windows generally used are the triangular and Hanning. The coefficients of

Resample DFT

DFT

frequency estimation algorithm. As a result, its use is not recommended.

**Figure 1.** DFT with control of the ADC sampling frequency

238 Power Quality Issues

**Figure 2.** DFT with signal resample

**5.3. Discrete fourier with window**

**5.2. Discrete fourier transform with signal resample**

the resampling process. Fig. 2 shows the block diagram of this strategy.

ADC

a Hanning window are computed from the following equation:

Frequency Estimator

Frequency Estimator

$$w[n] = \begin{cases} \frac{2n}{N-1}, & \text{if } 1 \le n \le \frac{N}{2};\\ \frac{2(N-n)}{N-1}, & \text{if } \frac{N+1}{2} \le n \le N-1; \end{cases} \tag{28}$$

for *N* odd.

### **5.4. Demodulation**

An interesting method based on demodulation technique for estimating time-varying har‐ monics is presented in [16]. This technique can provide very accurate estimates with a reasonable computational complexity.

The block diagram of the demodulation technique is depicted in Fig. 3. The LP blocks imple‐ ment identical low-pass filters and the blocks COS and SIN implement the demodulation signals expressed by

$$d\_{c\_k}[n] = \cos(k w\_0 n + \varphi\_k[n])\tag{29}$$

and

$$d\_{s\_k}[\nu] = \sin(k\pi\_0 n + \varphi\_k[\nu]),\tag{30}$$

respectively. The term *φ<sup>k</sup> n* control the instantaneous frequency of the demodulation signals (29)-(30). It is evaluated by

$$
\varphi \rho\_k[\boldsymbol{\nu}] = \varphi\_k[\boldsymbol{\nu} - 1] + \frac{k}{f\_s} (\boldsymbol{\nu}\_1[\boldsymbol{\nu}] - \boldsymbol{\Omega}\_0)\_\prime \tag{31}
$$

where *ψ*<sup>1</sup> *n* is the estimated fundamental frequency in rad.

The blocks AMP and PHAS implement, respectively, the expressions

$$
\hat{A}\_k[n] = 2\sqrt{y\_{cc\_k}^2[n] + y\_{ss\_k}^2[n]}\tag{32}
$$

**5.5. Non linear least squares**

euclidian norm of the following vector:

**6. Performance analysis**

considered:

where *v n* ~N(0, *σ* <sup>2</sup>

The nonlinear least squares (NLS) uses the same expressions of the linear least squares for evaluate the harmonics [18]. The advantage of this approach is the improving of the estimates related to the linear version, however, the additional searching of the optimal frequency

The NLS algorithm test several values of *w*0 near its nominal value in order to minimize the

Thus, with the optimal *w*0, the harmonic parameters are evaluates as presented in section 4.4.

In order to analyze the performance of the described techniques the following signal is

1 01 3 03 5 05 7 07 9 0 9 11 0 11 13 0 13 15 0 15

[ ]cos(21 [ ]) [ ]cos(23 [ ]) [ ]cos(25 [ ]) [ ],

f

between the fundamental component and the additive noise is 60 dB (it should be noted that the SNR of the signal obtained from a power system usually ranges between 50 and 70 dB [19]). Fig. 4 shows time estimations of the amplitude of the 3rd harmonic considering a 50% drop in the amplitude of signal when the fundamental frequency is equal to 60 Hz. Estimation delays of 2 cycles of the fundamental component are noted because the twocycles version of each technique was considered. However, when the fundamental frequency is set to 60.5 Hz such techniques exhibit significant errors in the estimates (time variations), as can be seen in Fig. 5. Otherwise, the time-varying techniques significantly improve the estimates. These results are depicted in Fig. 6. Table 1 shows the maximum of the absolute instantaneous error of all techniques after convergence of the algorithms (after the 50% drop in the amplitude of signal). The best results are achieved with the demodulation and NLS techniques. Considering only these last two techniques, the errors were evaluated when the fundamental frequency varies

*A n wn n A n wn n A n wn n vn*

[ ] [ ]cos( [ ]) [ ]cos(3 [ ]) [ ]cos(5 [ ]) [ ]cos(7 [ ]) [ ]cos(9 [ ]) [ ]cos(11 [ ]) [ ]cos(13 [ ]) [ ]cos(15 [ ])

*xn A n wn n A n wn n A n wn n A n wn n A n wn n A n wn n A n wn n A n wn n*

= ++ + + ++ + + ++ + + ++ + + + <sup>19</sup> 0 19 21 0 21 23 0 23

f

f

f

f

f

f

25 0 25

+ ++ + + ++

17 0 17

[ ]cos(17

*A n wn*

<sup>1</sup> [ ] ( ( [ ] [ ]) [ ]) [ ] *T T m mm m m* - **e I HH H H y** = - (34)

Parameters Estimation of Time-Varying Harmonics

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241

 f

 f

> f

[ ]) [ ]cos(19 [ ])

)is a white zero-meanGaussiannoise so thatthe signal-to-noise ratio (SNR)

*n A n wn n*

+ +

 f

 f

f

(35)

introduces additional delay in the technique and computational burden.

and

$$\hat{\phi}\_{k}[n] = -\arctan\left(\frac{y\_{ss\_{k}}[n]}{y\_{cc\_{k}}[n]}\right) \tag{33}$$

respectively, where *dck n* is the output of the low-pass filter at the top and *dsk n* is the output of the low-pass filter at the bottom in Fig. 3.

In this technique, it is applied a approach to control the demodulation signals (blocks COS and SIN) and the frequency response of the low-pass filters (blocks LP) by the power frequency estimate, which is implemented by the block FREQ. The low pass filters are finite impulse response (FIR) filters which are controlled by a frequency estimator.

**Figure 3.** Block diagram of the demodulation technique for time-varying harmonic estimation.

### **5.5. Non linear least squares**

where *ψ*<sup>1</sup> *n* is the estimated fundamental frequency in rad.

and

240 Power Quality Issues

The blocks AMP and PHAS implement, respectively, the expressions

*k*

f

of the low-pass filter at the bottom in Fig. 3.

FREQ

*n*

response (FIR) filters which are controlled by a frequency estimator.

<sup>ˆ</sup> 2 2 [] 2 [] [] *k k*

[ ] <sup>ˆ</sup> [ ] arctan , [ ]

= - ç ÷

respectively, where *dck n* is the output of the low-pass filter at the top and *dsk n* is the output

In this technique, it is applied a approach to control the demodulation signals (blocks COS and SIN) and the frequency response of the low-pass filters (blocks LP) by the power frequency estimate, which is implemented by the block FREQ. The low pass filters are finite impulse

LP

COS

LP

SIN

**Figure 3.** Block diagram of the demodulation technique for time-varying harmonic estimation.

*k k ss*

*y n*

ç ÷ è ø

*y n*

æ ö

*cc*

*An y n y n <sup>k</sup> cc ss* = + (32)

AMP

PHAS

(33)

The nonlinear least squares (NLS) uses the same expressions of the linear least squares for evaluate the harmonics [18]. The advantage of this approach is the improving of the estimates related to the linear version, however, the additional searching of the optimal frequency introduces additional delay in the technique and computational burden.

The NLS algorithm test several values of *w*0 near its nominal value in order to minimize the euclidian norm of the following vector:

$$\mathbf{e}[m] = \left(\mathbf{I} - \mathbf{H} (\mathbf{H}^T [m] \mathbf{H} [m])^{-1} \mathbf{H}^T [m] \right) \mathbf{y}[m] \tag{34}$$

Thus, with the optimal *w*0, the harmonic parameters are evaluates as presented in section 4.4.

### **6. Performance analysis**

In order to analyze the performance of the described techniques the following signal is considered:

$$\begin{aligned} x[n] &= A\_1[n] \cos(w\_0 n + \phi\_1[n]) + A\_3[n] \cos(3w\_0 n + \phi\_3[n]) \\ &+ A\_5[n] \cos(5w\_0 n + \phi\_5[n]) + A\_7[n] \cos(7w\_0 n + \phi\_7[n]) \\ &+ A\_9[n] \cos(9w\_0 n + \phi\_9[n]) + A\_{11}[n] \cos(11w\_0 n + \phi\_{11}[n]) \\ &+ A\_{13}[n] \cos(13w\_0 n + \phi\_{13}[n]) + A\_{15}[n] \cos(15w\_0 n + \phi\_{15}[n]) \\ &+ A\_{17}[n] \cos(17w\_0 n + \phi\_{17}[n]) + A\_{19}[n] \cos(19w\_0 n + \phi\_{19}[n]) \\ &+ A\_{21}[n] \cos(21w\_0 n + \phi\_{21}[n]) + A\_{23}[n] \cos(23w\_0 n + \phi\_{23}[n]) \\ &+ A\_{25}[n] \cos(25w\_0 n + \phi\_{25}[n]) + v[n] \end{aligned} \tag{35}$$

where *v n* ~N(0, *σ* <sup>2</sup> )is a white zero-meanGaussiannoise so thatthe signal-to-noise ratio (SNR) between the fundamental component and the additive noise is 60 dB (it should be noted that the SNR of the signal obtained from a power system usually ranges between 50 and 70 dB [19]).

Fig. 4 shows time estimations of the amplitude of the 3rd harmonic considering a 50% drop in the amplitude of signal when the fundamental frequency is equal to 60 Hz. Estimation delays of 2 cycles of the fundamental component are noted because the twocycles version of each technique was considered. However, when the fundamental frequency is set to 60.5 Hz such techniques exhibit significant errors in the estimates (time variations), as can be seen in Fig. 5. Otherwise, the time-varying techniques significantly improve the estimates. These results are depicted in Fig. 6. Table 1 shows the maximum of the absolute instantaneous error of all techniques after convergence of the algorithms (after the 50% drop in the amplitude of signal).

The best results are achieved with the demodulation and NLS techniques. Considering only these last two techniques, the errors were evaluated when the fundamental frequency varies between 59.5 Hz to 60.5 Hz for the 25th harmonic (See Fig. 7). Also, it is important to note that the improvement achieved by the DFT with hanning and triangular windows is significant compared with the standard DFT method as can be seen by Figs. 5 and 6. In order to better show this improvement, the errors, considering the DFT, DFT with triangular window and DFT with hanning window, were evaluated when the fundamental frequency varies between 59.5 Hz and 60.5 Hz for the 25th harmonic (Fig. 8).

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

LS

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

Goertzel

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

Demodulation

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

**Figure 5.** Estimation performance for the signal given by equation (35) in the case of a 50% drop in its amplitude for the 3*rd* harmonic when the fundamental frequency is set to be 60.5 Hz considering the steady-state methods.

DFT

Time (s)

Parameters Estimation of Time-Varying Harmonics

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243

Time (s)

Time (s)

Time (s)

0.2 0.3 0.4

0.2 0.3 0.4

0.2 0.3 0.4

0.2

0.3 0.4

Amplitude (p.u.)

Amplitude (p.u.)

Amplitude (p.u.)

Amplitude (p.u.)

**Figure 4.** Estimation performance for the signal given by equation (35) in the case of a 50% drop in its amplitude for the 3*rd* harmonic when the fundamental frequency is set to be 60 Hz considering the steady-state methods.

between 59.5 Hz to 60.5 Hz for the 25th harmonic (See Fig. 7). Also, it is important to note that the improvement achieved by the DFT with hanning and triangular windows is significant compared with the standard DFT method as can be seen by Figs. 5 and 6. In order to better show this improvement, the errors, considering the DFT, DFT with triangular window and DFT with hanning window, were evaluated when the fundamental frequency varies between

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

LS

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

Goertzel

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

Demodulation

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

**Figure 4.** Estimation performance for the signal given by equation (35) in the case of a 50% drop in its amplitude for the 3*rd* harmonic when the fundamental frequency is set to be 60 Hz considering the steady-state methods.

DFT

Time (s)

Time (s)

Time (s)

Time (s)

59.5 Hz and 60.5 Hz for the 25th harmonic (Fig. 8).

242 Power Quality Issues

0.2 0.3 0.4

0.2 0.3 0.4

0.2 0.3 0.4

0.2 0.3 0.4

Amplitude (p.u.)

Amplitude (p.u.)

Amplitude (p.u.)

Amplitude (p.u.)

**Figure 5.** Estimation performance for the signal given by equation (35) in the case of a 50% drop in its amplitude for the 3*rd* harmonic when the fundamental frequency is set to be 60.5 Hz considering the steady-state methods.

59.5 59.6 59.7 59.8 59.9 <sup>60</sup> 60.1 60.2 60.3 60.4 60.5 <sup>0</sup>

Demodulation (time-varying)

Parameters Estimation of Time-Varying Harmonics

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245

NLS

Frequency (Hz)

**Figure 7.** Maximum of the absolute instantaneous amplitude for the 25th harmonic when the fundamental frequency

DFT

DFT with triagular window DFT with hanning window

59.5 59.6 59.7 59.8 59.9 <sup>60</sup> 60.1 60.2 60.3 60.4 60.5 <sup>0</sup>

Frequency (Hz)

**Figure 8.** Maximum of the absolute instantaneous amplitude for the 25th harmonic when the fundamental frequency varies between 59.5 Hz to 60.5 Hz considering the DFT, DFT with triangular window and DFT with hanning window.

> DFT 4.7655 Goertzel 4.7655 LS 4.7655

**Technique Maximum Instantaneous Error**

0.5

10

20

30

Maximum Absolute Error (%)

40

50

60

varies between 59.5 Hz to 60.5 Hz considering the NLS and Demodulaton method.

1

1.5

Maximum Absolute Error (%)

2

2.5

3

3.5

**Figure 6.** Estimation performance for the signal given by equation (35) in the case of a 50% drop in its amplitude for the 3*rd* harmonic when the fundamental frequency is set tobe 60.5 Hz considering the time-varying methods.

**Figure 7.** Maximum of the absolute instantaneous amplitude for the 25th harmonic when the fundamental frequency varies between 59.5 Hz to 60.5 Hz considering the NLS and Demodulaton method.

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

DFT with the triangular window

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

NLS

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

Demodulation

0.2 0.4 0.6 0.8 <sup>1</sup> 1.2 1.4 1.6 0.1

**Figure 6.** Estimation performance for the signal given by equation (35) in the case of a 50% drop in its amplitude for the 3*rd* harmonic when the fundamental frequency is set tobe 60.5 Hz considering the time-varying methods.

DFT with the hanning window

Time (s)

Time (s)

Time (s)

Time (s)

0.2 0.3 0.4

0.2 0.3 0.4

0.2 0.3 0.4

0.2 0.3 0.4

Amplitude (p.u.)

Amplitude (p.u.)

Amplitude (p.u.)

Amplitude (p.u.)

244 Power Quality Issues

**Figure 8.** Maximum of the absolute instantaneous amplitude for the 25th harmonic when the fundamental frequency varies between 59.5 Hz to 60.5 Hz considering the DFT, DFT with triangular window and DFT with hanning window.



*grids* is pushing forward the development of new techniques as well as discussion of new

Although *smart grids* offers the opportunity to improve the quality, efficiency and reliability for power systems, the increase of disturbances levels is inevitable. Thus, new challenges

, Carlos A. Duque1

[1] Akagi, H. New trends in active filters for power conditioning, *IIEEE Trans. Ind. Appl.*,

[2] Watson, N. R, & Arrigala, J. Harmonics in large systems, *Electric Power System Re‐*

[3] Masoum, M. A. S, Moses, P. S, & Masoum, A. S. Derating of Asymmetric Three-Phase Transformers Serving Unbalanced Nonlinear Loads, *IEEE Trans. Power Deliv‐*

[4] Lai, L. L, Chan, W. L, Tse, C. T, & So, A. T. P. Real-time frequency and harmonic evaluation using artificial neural networks, *IEEE Trans. on Power Delivery*, Jan.

[5] Ribeiro, P. Time-Varying Waveform Distortions in Power Systems, Wiley-IEEE Press,

[6] Begovi, M. M, Djuri, c a. n. d P. M, Dunlap, c a. n. d S, & Phadke, A. G. Frequency tracking in power networks in the presence of harmonics, *IEEE Trans. on Power Deliv‐*

[7] Boashash, B. Estimating and interpreting the instantaneous frequency of a signal. I.

[8] George, T. A. Harmonic power flow determination using the fast Fourier transform,

Fundamentals, *Proceedings of the IEEE*, Apr (1992). , 80(4), 520-538.

*IEEE Trans. on Power Delivery*, Apr. (1991). , 2(2), 530-535.

and Eduardo A. B. da Silva2

Parameters Estimation of Time-Varying Harmonics

http://dx.doi.org/10.5772/53816

247

measurement standards for time-varying harmonics.

, Moisés V. Ribeiro1

related to the power quality will be introduced.

1 Federal University of Juiz de Fora, Brazil

2 Federal University of Rio de Janeiro, Brazil

November (1996). , 32(6), 1312-1322.

*ery*, October (2008). , 23(4), 2033-2041.

*search*, (2003). , 66, 15-29.

(1999). , 14(1), 52-59.

*ery*, Apr. (1993). , 8(2), 480-486.

(2009).

**Author details**

**References**

Cristiano A. G. Marques1

**Table 1.** Maximum of the absolute instantaneous error of all techniques after convergence of the algorithms.

### **7. What is next and needed?**

Most existing end-user equipment (computer, television, lamps, etc) emit almost exclusively at the lower odd integer harmonics, but there are indications that modern devices including certain types of distributed generators emit a broadband spectrum [11–14]. The measurement of these low levels of harmonics at higher frequencies will be more difficult than for the existing situation with higher levels and lower frequencies. This might require the development of new measurement techniques including a closer look at the frequency response of existing instru‐ ment transformers. Consequently, harmonic estimation of higher order harmonics will be very important and needed. In this case the sampling frequency should be increased to satisfy the Nyquist criterion and faster *analog to digital converter* (ADC) must be used to deal with this requirement.

Power electronic based photovoltaic solar and wind energy equipment may emit disturbances causing voltage fluctuations and unbalance. These types of electric sources will have large presence in the future grids very large. In order to deal with this new scenario, the harmonic estimation algorithms must be immune to higher voltage fluctuations and interharmonics.

An important issue associated with smart grid in regarding to harmonic estimation is the real time estimation of several harmonics instantaneously, including higher-order harmonics. Higher-order harmonics will be more and more important to estimate due its influence in sensitive electronics devices. Also, the dynamic and diversity of smart grid will demand different set of techniques to analyze the behavior of the time-varying harmonics. For deal with these issues, the use of reconfigurable hardware that allow the exchange of features between existing monitoring devices is of ultimate importance.

### **8. Concluding remarks**

Several methods and techniques were developed so far for estimating steady-state and timevarying harmonics. Although several techniques can deal with time-varying harmonics, the implementation of them is incipient. However, the needs and demands related to *smart* *grids* is pushing forward the development of new techniques as well as discussion of new measurement standards for time-varying harmonics.

Although *smart grids* offers the opportunity to improve the quality, efficiency and reliability for power systems, the increase of disturbances levels is inevitable. Thus, new challenges related to the power quality will be introduced.

### **Author details**

**Technique Maximum Instantaneous Error**

NLS 0.0842

Most existing end-user equipment (computer, television, lamps, etc) emit almost exclusively at the lower odd integer harmonics, but there are indications that modern devices including certain types of distributed generators emit a broadband spectrum [11–14]. The measurement of these low levels of harmonics at higher frequencies will be more difficult than for the existing situation with higher levels and lower frequencies. This might require the development of new measurement techniques including a closer look at the frequency response of existing instru‐ ment transformers. Consequently, harmonic estimation of higher order harmonics will be very important and needed. In this case the sampling frequency should be increased to satisfy the Nyquist criterion and faster *analog to digital converter* (ADC) must be used to deal with this

Power electronic based photovoltaic solar and wind energy equipment may emit disturbances causing voltage fluctuations and unbalance. These types of electric sources will have large presence in the future grids very large. In order to deal with this new scenario, the harmonic estimation algorithms must be immune to higher voltage fluctuations and interharmonics.

An important issue associated with smart grid in regarding to harmonic estimation is the real time estimation of several harmonics instantaneously, including higher-order harmonics. Higher-order harmonics will be more and more important to estimate due its influence in sensitive electronics devices. Also, the dynamic and diversity of smart grid will demand different set of techniques to analyze the behavior of the time-varying harmonics. For deal with these issues, the use of reconfigurable hardware that allow the exchange of features

Several methods and techniques were developed so far for estimating steady-state and timevarying harmonics. Although several techniques can deal with time-varying harmonics, the implementation of them is incipient. However, the needs and demands related to *smart*

between existing monitoring devices is of ultimate importance.

Demodulation (steady-state) 4.7655 DFT with hanning window 0.7479 DFT with triangular window 0.2296

Demodulation (time-varying) 0.0660

**Table 1.** Maximum of the absolute instantaneous error of all techniques after convergence of the algorithms.

**7. What is next and needed?**

requirement.

246 Power Quality Issues

**8. Concluding remarks**

Cristiano A. G. Marques1 , Moisés V. Ribeiro1 , Carlos A. Duque1 and Eduardo A. B. da Silva2

1 Federal University of Juiz de Fora, Brazil

2 Federal University of Rio de Janeiro, Brazil

### **References**


[9] Thorp, J. S, Phadke, A. G, & Karimi, K. J. Real-time voltage phasor measurements for static-state estimation, *IEEE Trans. Power App. Syst.*, Nov. (1985). , PAS-104(11), 3099-3106.

**Chapter 10**

**Evaluation of the Distortion**

**in Electric Networks**

Alejandro Pérez Vallés

http://dx.doi.org/10.5772/53373

**1. Introduction**

Patricio Salmerón Revuelta and

**and Unbalance Emission Levels**

Additional information is available at the end of the chapter

ically on harmonic and unbalance phenomena.

Electrical disturbances have important economic consequences for the consumer and the utilities, a fact which increases from the new electricity regulatory framework. Thus, Electric Power Quality, EPQ, has now become a priority within the field of electrical engineering. Power-quality deterioration is due to transient disturbances (voltage sags, voltage swells, impulses, etc.) and steady state disturbances (harmonic distortion, unbalance, and flicker). Among these are the so-called periodic disturbances such as distortion of the voltage and current waveforms, or unbalanced three-phase systems, [1-2]. This chapter is focused specif‐

These quality problems have entailed the need for measuring equipment to monitor the installation at the user side such as electric power quality analyzers, [3-7]. This equipment has a great number of quantities available relating to the harmonic distortion for each phase. Each measurement is usually composed of the voltage and current total harmonic distortion (THD) index, and RMS values of the total waveforms and the fundamental component. One problem with characterization of these data is representation of harmon‐ ic distortion when the installation has very different distortion levels in each phase. There are two choices: to consider the distortion level of each phase separately, managing three times more information, or to characterize the installation distortion using a global pa‐ rameter which considers the whole three-phase system, [5, 7]. The first approach is more interesting for analyzing the cause of the problems in an installation. The second is more

> © 2013 Revuelta and Vallés; licensee InTech. This is an open access article distributed under the terms of the Creative Commons Attribution License (http://creativecommons.org/licenses/by/3.0), which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Attribution License (http://creativecommons.org/licenses/by/3.0), which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

© 2013 Revuelta and Vallés; licensee InTech. This is a paper distributed under the terms of the Creative Commons


**Chapter 10**
